Electronic circuits including a MOSFET and a dual-gate JFET

ABSTRACT

Electronic circuits and methods are provided for various applications including signal amplification. An exemplary electronic circuit comprises a MOSFET and a dual-gate JFET in a cascode configuration. The dual-gate JFET includes top and bottom gates disposed above and below the channel. The top gate of the JFET is controlled by a signal that is dependent upon the signal controlling the gate of the MOSFET. The control of the bottom gate of the JFET can be dependent or independent of the control of the top gate. The MOSFET and JFET can be implemented as separate components on the same substrate with different dimensions such as gate widths.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a Continuation of U.S. patent application Ser. No.13/107,411 filed on May 13, 2011 now U.S. Pat No. 8,179,197 and entitled“Electronic Circuits Including a MOSFET and a Dual-Gate JFET” which is aDivisional application of U.S. patent application Ser. No. 12/686,573filed on Jan. 13, 2010 now U.S. Pat. No. 7,969,243 and also entitled“Electronic Circuits including a MOSFET and a Dual-Gate JFET” whichclaims the benefit of U.S. Provisional Patent Application No. 61/171,689filed on Apr. 22, 2009 and entitled “Electronic Circuits including aMOSFET and a Dual-Gate JFET and having a High Breakdown Voltage” each ofwhich is incorporated herein by reference. This application is alsorelated to U.S. patent application Ser. No. 12/070,019 filed on Feb. 13,2008 and entitled “High Breakdown Voltage Double-Gate SemiconductorDevice,” now U.S. Pat. No. 7,863,645 issued on Jan. 4, 2011, which isalso incorporated herein by reference.

BACKGROUND

1. Field of Invention

The present invention relates generally to semiconductor devices andmore particularly to semiconductor devices configured for powerapplications.

2. Related Art

Complementary metal-oxide semiconductor (CMOS) devices designed forradio-frequency (RF) power applications have traditionally required atradeoff between improved RF performance versus a higher breakdownvoltage. For example, the RF performance of a CMOS device may beimproved by reducing gate geometries (e.g., by using short channellengths). A smaller gate geometry, however, reduces the breakdownvoltage of the CMOS device. Because the reduced breakdown voltage limitsthe voltage swing available at the output of the CMOS device in anamplifier configuration, such CMOS devices are less useful in powerapplications.

In one approach to the breakdown voltage problem, CMOS devices may bedesigned for greater current drive with a lower voltage swing. Greatercurrent drive may, however, require the width of a transistor in theCMOS device to be made large thus presenting an undesired capacitiveload to the driving circuit.

Another approach to the breakdown voltage problem uses LaterallyDiffused Metal-Oxide-Semiconductor (LDMOS) transistors. LDMOStransistors have a drift region between an active region and a drain.The drift region is lightly doped and experiences the largest voltageswings. Because the doping concentration in the drift region is limitedby the breakdown voltage requirements, LDMOS devices tradeoff a higherbreakdown voltage for a higher total resistance of the drain-currentflowing between the drain and the source terminals (known as theon-state resistance).

Another approach to the breakdown voltage problem uses devices withthicker and higher resistivity substrates. These devices may offerhigher-voltage performance but also introduce higher on-state losses.These devices include Reduced Surface Field (RESURF) devices in whichthe depletion region of the substrate diode interacts with the depletionregion of the lateral diode to reduce the surface field. In thesedevices, the voltage breakdown is increased because of the lateralwidening of the depletion zone.

There is, therefore, a need for a high breakdown voltage semiconductordevice that provides improved RF capability and higher power as comparedto conventional semiconductor devices.

SUMMARY

The present invention provides various electronic circuits for use aspower amplifiers for amplifying input signals. An exemplary circuitcomprises a MOSFET and a JFET, both including a source and a drain,where the source of the JFET is directly coupled to the drain of theMOSFET. The MOSFET also includes a gate, while the JFET also includesboth a top gate and a bottom gate. The gates of the MOSFET and of theJFET, in some embodiments, have different widths.

In various embodiments the top gate of the JFET is coupled to the gateof the MOSFET. In some of these embodiments the bottom gate of the JFETis also coupled to the gate of the MOSFET, and in some of theseembodiments the top and bottom gates of the JFET are both coupled to aDC bias source.

In various embodiments of the exemplary circuit the top gate of the JFETis coupled to the bottom gate of the JFET and both gates are independentof the gate of the MOSFET. In some of these embodiments the top andbottom gates of the JFET are both coupled to a DC bias source, while inother of these embodiments the top and bottom gates of the JFET are bothcoupled to ground. In still further of these embodiments the top gate ofthe JFET is coupled to a first DC bias source and/or the bottom gate ofthe JFET is coupled to a second DC bias source or ground.

The present invention is also directed to various devices. An exemplarydevice comprises a transceiver coupled to a power amplifier as set forthabove. The transceiver, in various embodiments, is configured to producea signal having a frequency in the range of about 700 MHz to about 2.5GHz or to produce a signal having a frequency in the range of about 150MHz to about 6 GHz. In some embodiments the transceiver is disposed on asame substrate as the MOSFET and the JFET. Various embodiments furthercomprise an output matching circuit coupled to the drain of the JFET.

Further, the present invention also provides methods for signalamplification. An exemplary method comprises controlling a gate of aMOSFET with a first signal, controlling a top gate of a JFET with asecond signal, and controlling a bottom gate of the JFET with a thirdsignal, where the JFET is in a cascode configuration with the MOSFET. Invarious embodiments the second signal is dependent on the first signaland in some of these embodiments the third signal is dependent on thesecond signal. Similarly, in various embodiments the second signal isindependent on the first signal and in some of these embodiments thethird signal is dependent on the second signal.

BRIEF DESCRIPTION OF THE DRAWINGS

Elements in the figures are illustrated for simplicity and clarity andare not drawn to scale. The dimensions of some of the elements may beexaggerated relative to other elements to help improve the understandingof various embodiments of the invention.

FIG. 1 illustrates an exemplary cross section of a double-gatesemiconductor device comprising a MOS gate, a junction gate and twoadjacent N+ regions, according to an embodiment of the presentinvention.

FIG. 2 illustrates an exemplary cross section of a double-gatesemiconductor device comprising a MOS gate, a junction gate and two N+regions coupled using a conducting layer, according to an embodiment ofthe present invention.

FIG. 3 illustrates an exemplary cross section of a double-gatesemiconductor device comprising a MOS gate, a junction gate, and asingle N+ region disposed between the MOS gate and the junction gate,according to an embodiment of the present invention.

FIG. 4 illustrates an exemplary cross section of the double-gatesemiconductor device of FIG. 3 in a second mode of operation, accordingto an embodiment of the present invention.

FIG. 5 illustrates an exemplary circuit diagram of the double-gatesemiconductor devices of FIGS. 1-3 and 6, according to an embodiment ofthe present invention.

FIG. 6 illustrates an exemplary cross section of a double-gatesemiconductor device comprising a MOS gate and a junction gate,according to an embodiment of the present invention.

FIG. 7 provides a circuit diagram for an exemplary electronic circuitcomprising a MOSFET and a dual-gate JFET, according to an embodiment ofthe present invention.

FIGS. 8A and 8B are cross sections of exemplary electronic circuits,each comprising a MOSFET and a dual-gate JFET where the MOSFET and theJFET are distinct, according to two embodiments of the presentinvention.

FIGS. 9-15 provide circuit diagrams for several exemplary electroniccircuits comprising a MOSFET and a dual-gate JFET, according to variousembodiments of the present invention.

FIG. 16 provides a flowchart representation of an exemplary method foramplifying a signal with a MOSFET and a dual-gate JFET in a cascodeconfiguration.

DETAILED DESCRIPTION

The present disclosure is directed to double-gate semiconductor devicescharacterized by high breakdown voltages that allow for a largeexcursion of the output voltage, making these semiconductor devicesuseful for power applications, such as power amplification. Thedouble-gate semiconductor devices disclosed herein comprise ametal-oxide-semiconductor (MOS) gate and a junction gate, in which thebias of the junction gate may be a function of the gate voltage of theMOS gate. The breakdown voltage of such a double-gate semiconductordevice is the sum of the breakdown voltages of the MOS gate and thejunction gate. Because an individual junction gate has an intrinsicallyhigh breakdown voltage, the breakdown voltage of the double-gatesemiconductor device is higher than the breakdown voltage of anindividual MOS gate.

The double-gate semiconductor device provides improved RF capability inaddition to operability at higher power levels as compared toconventional complementary metal-oxide semiconductor (CMOS) devices. Thedouble-gate semiconductor device may be fabricated substantially onand/or in a substrate using techniques of semiconductor fabricationknown in the art and may use standard fabrication processes for CMOS andlogic devices with minor modifications in the process flow.

A MOS gate may include a metal-oxide-semiconductor structure that, whena voltage is applied to the MOS gate, modifies the charge distributionin a semiconductor structure, thus controlling the conductivecharacteristics of the semiconductor structure. The MOS gate can thusfunction as an electrically-controlled gate or switch. This type of gatemay be found in a metal-oxide-semiconductor field effect transistor(MOSFET) device. A junction gate includes a region of a channel ofsemiconductor material that has doping characteristics that are oppositethat of the rest of the channel such that when a voltage is applied tothe junction gate the charge distribution in the channel is modified andthereby controls the conductive characteristics of the channel. Thejunction gate can thus function as an electrically-controlled gate orswitch. This type of gate may be found in a junction field effecttransistor (JFET). The effective resistance of the junction gate is theresistance of the channel as controlled by the voltage of the junctiongate.

Double-gate semiconductor devices disclosed herein may be fabricated toinclude one or more implantation regions between the MOS gate and thejunction gate. Embodiments without an implantation region between theMOS gate and the junction gate may provide a higher spatial densityconfiguration for the double-gate semiconductor device than embodimentsthat include one or more implantation regions between the MOS gate andthe junction gate. The principles of operation of these variousembodiments are similar, except that a depletion region between the MOSgate channel and a drift region is modified.

FIG. 1 illustrates an exemplary cross section of a double-gatesemiconductor device comprising a MOS gate, a junction gate and twoadjacent N+ regions (i.e., implantation regions). Double-gatesemiconductor device 100 may be formed from regions and/or layers ofdoped silicon, polysilicon, metal, and insulating layers usingsemiconductor fabrication techniques known in the art. It will beunderstood that the term, “oxide layer,” as used herein, is a term ofart that refers to any suitable insulating layer for use as the barrierlayer in the MOS device, whether or not it happens to include oxygen.This term of art came about because the layer was traditionally formedof silicon dioxide, but in more recent years has come to also befabricated from other materials, such as low-k dielectric materials,some of which do not include oxygen.

Double-gate semiconductor device 100 comprises P− substrate 110, a N−well 120 formed in the P− substrate 110, N+ source 130, gate 140, oxidelayer 150, N+ region 160, N+ region 162, P+ gate 170, and N+ drain 180.As used herein, the “+” symbol indicates strong doping of theconductivity type indicated (e.g., N+ indicating N type, strong doping)and the “−” symbol indicates weak doping of the conductivity typeindicated (e.g., P− indicating P type, weak doping).

Electrical signals, such as V_(g1) and control voltage V_(g2), may becoupled to gate 140 and P+ gate 170, respectively. Electrical signalsmay also be coupled to N+ source 130, N+ region 160, N+ region 162 andN+ drain 180 using additional polysilicon layers (not shown) or metallayers (not shown) disposed on a surface of each of the N+ source 130,N+ region 160, N+ region 162 and N+ drain 180 using semiconductorfabrication techniques known in the art.

Double-gate semiconductor device 100 includes an N-type MOS Field EffectTransistor (also known as a N-channel MOSFET) formed by P− substrate110, N+ source 130, and N+ region 160, gate 140, and oxide layer 150.The double-gate semiconductor device 100 also includes an N-channelJunction Field Effect Transistor (also known as an N-type JFET) formedby P− substrate 110, N− well 120, N+ region 162, P+ gate 170 and N+drain 180. In this embodiment, N+ region 160 and N+ region 162 areadjacent and N+ region 162 is disposed substantially in N− well 120.

Alternatively, the elements of the double-gate semiconductor device 100may be configured so that the double-gate semiconductor device 100comprises a P-type MOS gate including a P-channel junction gate. In suchan embodiment, some of the regions and/or layers of doped silicon mayhave a different doping, according to semiconductor fabricationtechniques known in the art.

The double-gate semiconductor device 100 may be considered to operate intwo modes. A first mode, illustrated in FIG. 1, is indicated by V_(g1)>athreshold voltage V_(th) and |V_(g2)−V_(PI)|≈0 (i.e., the absolute valueof V_(g2)−V_(PI) is approximately 0). V_(g1) is a voltage at the gate140, V_(g2) is a voltage at the P+ gate 170, V_(th) is a thresholdvoltage for the gate 140, and V_(PI) is a voltage at N+ region 162. Inthe first mode a voltage V_(g1) is applied to gate 140 that is greaterthan V_(th) so that the MOS gate is “on.” A control voltage V_(g2) isapplied to P+ gate 170 so that the junction gate is biased with a lowpotential difference between control voltage V_(g2) and a voltage V_(PI)of the N+ region 162. The P+ gate 170 thus presents a low resistance,R_(on), to the current flow. In the first mode, the semiconductor device100 conducts a current between N+ source 130 and N+ drain 180. In thesecond mode, the semiconductor device 100 does not conduct the current.

Returning to FIG. 1, in the second mode a negative control voltageV_(g2) is applied to P+ gate 170 and the depletion region under P+ gate170 extends into a channel (not shown) in N− well 120. When the controlvoltage V_(g2) applied to P+ gate 170 is such that |V_(g2)−V_(PI)| isgreater than a pinch off voltage, V_(off), the channel is fully depletedunder the P+ gate 170 and no current flows between the N+ region 162 andN+ drain 180. Likewise, in the second mode, no current flows between N+source 130 and N+ drain 180.

When a control voltage V_(g2) is applied to P+ gate 170 such that|V_(g2)−V_(PI)|≈0 (corresponding to the first mode), the channel is openand a current of majority carriers may flow between N+ region 162 and N+drain 180. The P+ gate 170 (the junction gate) may, therefore, behaveequivalently to a variable resistor with a high effective resistance,R_(off), that allows little or no current flow between N+ source 130 andN+ drain 180 when |V_(g2)−V_(PI)|>V_(off), and a low effectiveresistance, R_(on), allowing maximum current flow when|V_(g2)−V_(PI)|≈0.

The double-gate semiconductor device 100 may include a device with adouble gate in which the control voltage V_(g2) at P+ gate 170 (thejunction gate) may be a function of the voltage V_(g1) at gate 140 (theMOS gate). The MOS gate and the junction gate may both be dynamicallybiased in the “on” state or “off” state at the same time using a controlcircuitry described with reference to FIG. 5.

The high effective resistance, R_(off), in the second mode of operationallows the P+ gate 170 to sustain a high voltage and limits the voltagepotential between gate 140 and N+ region 160 to less than the MOS gatebreakdown voltage. Because the breakdown voltage of the double-gatesemiconductor device 100 is the sum of the breakdown voltages of the MOSgate and the P+ gate 170, the intrinsically high breakdown voltage ofthe P+ gate 170 provides the high breakdown voltage of the double-gatesemiconductor device 100.

The control voltage V_(g2) may be adjusted using the control circuitryand may depend on the pinch-off voltage, V_(off). The control circuitrymay comprise a capacitor (not shown) configured to couple a RF signalfrom gate 140 to P+ gate 170. To limit the distance between gate 140 andP+ gate 170, the capacitor may be implemented with multiple stackedmetal layers in parallel between the gate 140 and P+ gate 170.

FIG. 2 illustrates an exemplary cross section of a double-gatesemiconductor device comprising a MOS gate, a junction gate and two N+regions coupled using a conducting layer. Double-gate semiconductordevice 200 may be formed from regions and/or layers of doped silicon,polysilicon, metal, and insulating layers using semiconductorfabrication techniques known in the art.

Double-gate semiconductor device 200 comprises P− substrate 110, a N−well 120 formed in the P− substrate 110, N+ source 130, gate 140, oxidelayer 150, N+ region 260, N+ region 262, conducting layer 265, P+ gate170, and N+ drain 180. Conducting layer 265 may be a polysilicon layer,a metal layer or another conducting layer known in the art. Asillustrated in FIG. 2, N+ region 260 and N+ region 262 are separated bya region of P− substrate 110, and N+ region 262 is disposedsubstantially in N− well 120.

As discussed herein with respect to double-gate semiconductor device200, electrical signals, such as V_(g1) and control voltage V_(g2), maybe coupled to gate 140 and P+ gate 170, respectively. Electrical signalsmay also be coupled to N+ source 130, N+ region 260, N+ region 262 andN+ drain 180 using additional polysilicon layers (not shown) or metallayers (not shown) disposed on a surface of each of the N+ source 130,N+ region 260, N+ region 262 and N+ drain 180 using semiconductorfabrication techniques known in the art.

Double-gate semiconductor device 200 includes an N-type MOSFET formed byP− substrate 110, N− well 120, N+ source 130, and N+ region 260, gate140, and oxide layer 150. The double-gate semiconductor device 200 alsoincludes an N-channel JFET formed by P− substrate 110, N− well 120, N+region 262, P+ gate 170 and N+ drain 180. In this embodiment, N+ region260 and N+ region 262 are coupled using conducting layer 265.

Alternatively, the elements of the double-gate semiconductor device 200may be configured so that the double-gate semiconductor device 200comprises a P-type MOS gate including a P-channel junction gate or anN-type MOS gate including a P-channel junction gate or a P-type MOS gateincluding a N-channel junction gate. In such an embodiment, some of theregions and/or layers of doped silicon may have a different doping,according to semiconductor fabrication techniques known in the art.

The double-gate semiconductor device 200 may be considered to operateanalogously to the two modes as described herein with respect to FIG. 1.A first mode is indicated by V_(g1)>a threshold voltage V_(th) and|V_(g2)−V_(PI)|≈0, where V_(PI) is a voltage at N+ region 262. In thefirst mode, a voltage V_(g1) is applied to gate 140 that is greater thanV_(th) so that the MOS gate is “on.” A control voltage V_(g2) is appliedto P+ gate 170 so that the junction gate is biased with a low potentialdifference between control voltage V_(g2) and a voltage V_(PI) of the N+region 262. The P+ gate 170 thus presents a low resistance, R_(on), tothe current flow. In the first mode, the semiconductor device 200conducts a current between N+ source 130 and N+ drain 180. In the secondmode, the semiconductor device 200 does not conduct the current.

When a control voltage V_(g2) is applied to P+ gate 170 such that|V_(g2)−V_(PI)|≈0 (corresponding to the first mode), the channel is openand a current of majority carriers may flow between N+ region 262 and N+drain 180. The P+ gate 170 (the junction gate) may, therefore, behaveequivalently to a variable resistor with a high effective resistance,R_(off), that allows little or no current flow between N+ source 130 andN+ drain 180 when |V_(g2)−V_(PI)|>V_(off), and a low effectiveresistance, R_(on), allowing maximum current flow when|V_(g2)−V_(PI)|≈0.

The double-gate semiconductor device 200 may include a device with adouble-gate in which the control voltage V_(g2) at P+ gate 170, thejunction gate, may be a function of the voltage V_(g1) at gate 140. TheMOS gate and the junction gate may both be dynamically biased in the“on” state or “off” state at the same time using a control circuitrydescribed with reference to FIG. 5. The control circuitry may include acapacitor (not shown) configured to couple a RF signal from gate 140 toP+ gate 170, as described with reference to FIG. 1.

In the second mode of operation, the high effective resistance, R_(off),allows the P+ gate 170 to sustain a high voltage and limits the voltagepotential between gate 140 and N+ region 260 to less than the MOS gatebreakdown voltage. Because the breakdown voltage of the double-gatesemiconductor device 200 is the sum of the breakdown voltages of the MOSgate and the P+ gate 170, the intrinsically high breakdown voltage ofthe P+ gate 170 provides the high breakdown voltage of the double-gatesemiconductor device 200.

FIG. 3 illustrates an exemplary cross section of a double-gatesemiconductor device comprising a MOS gate and a junction gate and asingle N+ region disposed between the MOS gate and the junction gate.Double-gate semiconductor device 300 may be formed from regions and/orlayers of doped silicon, polysilicon, metal, and insulating layers usingsemiconductor fabrication techniques known in the art. Double-gatesemiconductor device 300 comprises P− substrate 110, a N− well 120formed in the P− substrate 110, N+ source 130, gate 140, oxide layer150, N+ region 360, P+ gate 170, and N+ drain 180. As illustrated inFIG. 3, N+ region 360 is disposed substantially in the N− well 120.

As described with reference to FIGS. 1-2, electrical signals, such asV_(g1) and control voltage V_(g2), may be coupled to gate 140 and P+gate 170, respectively. Electrical signals may also be coupled to N+source 130, N+ region 360 and N+ drain 180 using additional polysiliconlayers (not shown) or metal layers (not shown) disposed on a surface ofeach of the N+ source 130, N+ region 360 and N+ drain 180 usingsemiconductor fabrication techniques known in the art.

Double-gate semiconductor device 300 includes an N-type MOS gate formedby P− substrate 110, gate 140, and oxide layer 150. The double-gatesemiconductor device 300 also includes an N-channel JFET formed by P−substrate 110, N− well 120, N+ region 360, P+ gate 170 and N+ drain 180.In this embodiment, the N+ region 360 is a source of the N-channel JFETand abuts the N-type MOS gate, the N-type MOS gate comprising gate 140and oxide layer 150.

The double-gate semiconductor device 300 may be considered to operateanalogously to the two modes as described herein with respect to FIGS.1-2. A first mode is indicated by V_(g1)>a threshold voltage V_(th) and|V_(g2)−V_(PI)|≈0, where V_(PI) is a voltage at N+ region 360. In thefirst mode a voltage V_(g1) is applied to gate 140 that is greater thanV_(th) so that the MOS gate is “on.” A control voltage V_(g2) is appliedto P+ gate 170 so that the junction gate is biased with a low potentialdifference between control voltage V_(g2) and a voltage V_(PI) of the N+region 360. The P+ gate 170 thus presents a low resistance, R_(on), tothe current flow. In the first mode, the semiconductor device 300conducts a current between N+ source 130 and N+ drain 180. In the secondmode, the semiconductor device 300 does not conduct the current.

When a control voltage V_(g2) is applied to P+ gate 170 such that|V_(g2)−V_(PI)|≈0 (corresponding to the first mode), the channel is openand a current of majority carriers may flow between N+ region 360 and N+drain 180. The P+ gate 170 (the junction gate) may, therefore, beconsidered as behaving equivalently to a variable resistor with a higheffective resistance, R_(off), that allows little or no current flowbetween N+ source 130 and N+ drain 180 when |V_(g2)−V_(PI)|>V_(off), anda low effective resistance, R_(on), allowing maximum current flow when|V_(g2)−V_(PI)|≈0.

As described with reference to FIGS. 1-2, the double-gate semiconductordevice 300 may be considered to be a device with a double-gate in whichthe control voltage V_(g2) at P+ gate 170, the junction gate, may be afunction of the voltage V_(g1) at gate 140. The MOS gate and thejunction gate may both be dynamically biased in the “on” state or “off”state at the same time using a control circuitry described withreference to FIG. 5. The control circuitry may comprise a capacitor (notshown) configured to couple a RF signal from gate 140 to P+ gate 170, asdescribed with reference to FIG. 1.

In the second mode of operation, the high effective resistance, R_(off),allows the P+ gate 170 to sustain a high voltage and limits the voltagepotential between gate 140 and N+ region 360 to less than the MOS gatebreakdown voltage. Because the breakdown voltage of the double-gatesemiconductor device 300 is the sum of the breakdown voltages of the MOSgate and the P+ gate 170, the intrinsically high breakdown voltage ofthe P+ gate 170 provides the high breakdown voltage of the double-gatesemiconductor device 300.

FIG. 4 illustrates an exemplary cross section of the double-gatesemiconductor device 300 of FIG. 3 in a second mode of operation. Thedescription herein of the double gate semiconductor device 300 in asecond mode of operation applies analogously to the second mode ofoperation of the double-gate semiconductor devices 100 and 200 describedwith reference to FIGS. 1-2, respectively.

In the second mode of operation, the voltage V_(g1) applied to gate 140is lower than the threshold voltage, V_(th), so that the MOS gate is“off.” A control voltage V_(g2) is applied to the P+ gate 170 so thatthe junction gate is biased near the pinch-off voltage, V_(off), byusing a high potential difference between V_(g2) and a voltage V_(PI) ofthe N+ region 360. The P+ gate 170 thus presents a high effectiveresistance, R_(off), to the current flow in a drift region, such asdrift region 420 illustrated in FIG. 4. The high effective resistance,R_(off), results from a depletion region extending under and around theP+ gate 170, such as depletion region 410 illustrated in FIG. 4.

The high effective resistance, R_(off), in the second mode of operationallows the P+ gate 170 to sustain a high voltage and limits the voltageswing at gate 140 to less than the MOS gate breakdown voltage. Thesecond mode of operation effectively protects the gate 140 from voltagesgreater than the breakdown voltage. Because the breakdown voltage of thedouble-gate semiconductor device 300 is the sum of the breakdownvoltages of the MOS gate and the P+ gate 170, the intrinsically highbreakdown voltage of the P+ gate 170 provides the high breakdown voltageof the double-gate semiconductor device 300.

FIG. 5 illustrates an exemplary circuit diagram of the double-gatesemiconductor devices of FIGS. 1-2. The circuit 500 comprises N-channelJFET 510, N-channel MOSFET 520, and control circuitry 530. The controlcircuitry 530 provides a control voltage V_(g2) to the gate of N-channelJFET 510 that may be a function of the voltage V_(g1) of the N-channelMOSFET 520. The control circuitry 530 functions to dynamically bias boththe N-channel MOSFET 520 and N-channel JFET 510 in the “on” state or the“off” state at the same time. Control circuitry 530 may be a capacitorthat may couple a RF signal from the gate of the N-channel MOSFET to thegate of the N-channel JFET.

The control circuitry 530 provides the control voltage V_(g2) to biasN-channel JFET 510 so that the R_(off) effective resistance is a maximumvalue when the N-channel MOSFET is “off” (i.e., V_(g1)<V_(th)).Typically, the control voltage V_(g2) biases N-channel JFET 510 close tothe pinch-off voltage, \T_(off). When the N-channel MOSFET 520 is “on”(i.e., V_(g1)>V_(th)), then control circuitry 530 provides the controlvoltage V_(g2) to bias N-channel JFET 510 so that the R_(on) effectiveresistance is minimal and the current flow is a maximum. A large rangeof R_(on) to R_(off) effective resistance variation allows a largeexcursion of voltage at the drain of the N-channel JFET 510 and acorresponding high power capability for the double-gate semiconductordevices described with reference to FIGS. 1-2. The double-gatesemiconductor devices described with reference to FIGS. 1-2 may also berepresented by a circuit diagram similar to circuit 500 in whichN-channel junction gate 510 may be substituted with a P-channel junctiongate (not shown) and N-channel MOS gate 520 may be substituted with aP-channel MOS gate (not shown).

FIG. 6 illustrates a cross section of a double-gate semiconductordevice, according to an alternative embodiment of the invention. In thisembodiment, the double-gate semiconductor device 600 may be fabricatedin a higher spatial density configuration than the embodiments describedwith reference to FIGS. 1-4. As illustrated in FIG. 6, double-gatesemiconductor device 600 does not include a N+ region such as the N+region 160, N+ region 162, N+ region 260, N+ region 262 and N+ region360 described with reference to FIGS. 1-4. Thus, the double-gatesemiconductor device 600 is fabricated without the common implantationof an N+ region between the MOS gate and the junction gate. Theprinciple of operation of the double-gate semiconductor device 600 isanalogous to the principles of operation of the double-gatesemiconductor devices 100, 200 and 300 described with reference to FIGS.1-3, including the description of the second mode of operation describedwith reference to FIG. 4.

Double-gate semiconductor device 600 may be formed from regions and/orlayers of doped silicon, polysilicon, metal, and insulating layers usingsemiconductor fabrication techniques known in the art. The double-gatesemiconductor device 600 comprises P− substrate 110, a N− well 120formed in the P− substrate 110, N+ source 130, gate 140, oxide layer150, P+ gate 170 and N+ drain 180.

Electrical signals, such as V_(g1) and control voltage V_(g2), may becoupled to gate 140, and P+ gate 170, respectively. Electrical signalsmay be coupled to N+ source 130 and N+ drain 180 using additionalpolysilicon layers (not shown) or metal layers (not shown) disposed on asurface of each of the N+ source 130 and N+ drain 180 usingsemiconductor fabrication techniques known in the art.

The double-gate semiconductor device 600 may be considered to operateanalogously to the two modes of operation described with reference toFIGS. 1-4. In a first mode, a current conducts between N+ source 130 andN+ drain 180. In a second mode, the current does not conduct. In thefirst mode, a voltage V_(g1) is applied to gate 140 that is greater thana threshold voltage V_(th) (not shown). A control voltage V_(g2) isapplied to the P+ gate 170, thus presenting a low effective resistance,R_(on), to the current flow.

In the second mode of operation, the voltage V_(g1) applied to gate 140is lower than a threshold voltage, V_(th) and a control voltage V_(g2)is applied P+ gate 170, thus presenting a high effective resistance,R_(off), to the current flow. The high effective resistance, R_(off),results from a depletion region, similar to the depletion region 410described with reference to FIG. 4, that extends under and around P+gate 170.

FIG. 7 provides a circuit diagram for an exemplary electronic circuit700 for amplifying an input signal such as an RF signal. The electroniccircuit 700 comprises a MOSFET 705 and a dual-gate JFET 710 in a cascodeconfiguration. In the circuit 700 the JFET 710 functions as a variableresistor.

The MOSFET 705 and dual-gate JFET 710 are distinct transistors. As usedherein, two transistors are defined as distinct unless the transistorsshare a common implantation region. As an example, N+ regions 260 and262 (FIG. 2) are drain and source, respectively, of distincttransistors. As another example, N+ regions 160 and 162 (FIG. 1) aredrain and source, respectively, of transistors that are not distinctsince the two share a N+ implantation region.

The MOSFET 705 includes a drain and a source, and in operation thesource is coupled to a power supply such as V_(DD). The MOSFET 705 iscontrolled by a gate which, in operation, receives an input signal, forexample an RF signal, from a signal source such as transceiver 715.Various embodiments of circuit 700 include an input matching circuit 720between the transceiver 715 and the gate of the MOSFET 705 to match theimpedances on either side thereof. An exemplary matching circuit 720comprises a capacitor and an inductor where the capacitor is coupledbetween ground and a node between the transceiver 715 and the gate ofthe MOSFET 705, and the inductor is disposed in-line between the nodeand the gate of the MOSFET 705. In various embodiments the gate lengthof the MOSFET 705, i.e. the length of the gate implant located betweenthe source and the drain, is less than one micron. It is noted that gatewidth is the dimension of the gate in the plane of the substratemeasured perpendicular to the gate length. In various embodiments, theMOSFET 705 can be a NMOSFET or a PMOSFET.

The signal source, such as transceiver 715, is disposed on the samesubstrate as the MOSFET 705 and the dual-gate JFET 710, in someembodiments. In further embodiments, the signal source produces a signalwith a frequency in the range of about 700 MHz to about 2.5 GHz. Infurther embodiments, the signal source produces a signal with afrequency in the range of about 150 MHz to about 6 GHz.

The dual-gate JFET 710 comprises a source and a drain electricallyconnected by a channel that is controlled by two gates, a top gate 725and a bottom gate 730 disposed above and below the channel,respectively. In various embodiments, the dual gate JFET 710 can be aNJFET or a PJFET. In various embodiments the dual-gate JFET 710comprises a sub-micron gate length. The drain of the dual-gate JFET 710is coupled to an antenna 735 or another device configured for signaltransmission. In some embodiments the antenna 735 is coupled to thedrain of the dual-gate JFET 710 by an output matching circuit 740 formedwith passive networks, also provided to match impedances.

The source of the dual-gate JFET 710 is coupled to the drain of theMOSFET 705. In some embodiments, the source of the dual-gate JFET 710 isdirectly coupled to the drain of the MOSFET 705. As used herein,“directly coupled” means that there are no active components inelectrical communication between the coupled transistors. In someembodiments, the source of the dual-gate JFET 710 is coupled to thedrain of the MOSFET 705 through vias and a trace such as conductinglayer 265 (FIG. 2). In some embodiments a point between the source ofthe dual-gate JFET 710 and the drain of the MOSFET 705 comprises acommon node (CN) point. As shown in FIG. 7, the electronic circuit 700can also comprise, in some instances, an optional common node circuit750 coupled between the common node point and ground.

As noted above, the JFET 710 is controlled by a top gate 725 and abottom gate 730. In various embodiments, the top and bottom gates 725,730 are dependent (e.g. commonly controlled) or independent, and can becontrolled by ground, a DC bias, the input signal applied to the gate ofthe MOSFET 705, or the input signal plus a DC bias. Various exemplaryways to control the top and bottom gates 725, 730 are discussed withreference to FIGS. 9-15. In the example provided by FIG. 7, the top andbottom gates 725, 730 are commonly controlled by the output of anoptional JFET gate circuit 745 which is analogous to control circuit 530(FIG. 5).

The JFET gate circuit 745 serves to improve the performance ofembodiments of the invention that are used as a power amplifier. Thebias of the bottom gate 730 determines the voltage of the top gate 725to pinch off the JFET 710 where the pinch-off voltage of the JFET 710 isthe limit value for the drain of the MOSFET 705. An appropriate valuefor the bottom gate 730 bias is one that allows that the pinch-offvoltage of the JFET 710 to protect the MOSFET 705 in its reliable zone.In some embodiments the top gate 725 of the JFET 710 is maintained at0V. But the large gate-to-source and gate-to-drain capacitances couplethe large voltage of the drain and of the source onto the gate voltage,reducing the efficiency of the R_(off) and R_(on) variation of the JFET710. The function of the JFET gate circuit 745 is to cancel thesesignals on the top gate 725 by applying an opposing signal.

As shown in FIG. 7, the electronic circuit 700 can also comprise, insome instances, an optional common node circuit 750 coupled between thecommon node point and ground. The common node circuit 750 also serves toimprove the performance of embodiments of the invention that are used asa power amplifier. The common node circuit 750 compensates for theeffect of the gate-to-drain capacitance of the MOSFET 705 and thegate-to-source capacitance of the JFET 710. The common node circuit 750can be, in some embodiments, a single inductance or a serialinductor-capacitor (LC) network configured to resonate with the notedcapacitances of the MOSFET 705 and the JFET 710 at the particularfrequency.

FIG. 8A provides a cross section of an exemplary electronic circuit 800comprising a MOSFET 805 and a dual-gate JFET 810 where the MOSFET 805and the JFET 810 comprise distinct transistors. As in previousembodiments, the MOSFET 805 and the dual-gate JFET 810 can be formedfrom regions and/or layers of doped silicon, polysilicon, variousmetals, and various insulating layers using semiconductor fabricationtechniques known in the art. In this example, a source 815 of thedual-gate JFET 810 is directly coupled to a drain 820 of the MOSFET 805by a metal layer 825 and vias 830. As distinct transistors, the MOSFET805 and a dual-gate JFET 810 can be implemented at different locationson the same substrate and with different dimensions, such as differentwidths.

The JFET 810 additionally comprises a drain 835, a top gate 840, and abottom gate 845. The top gate 840 and bottom gate 845 are disposed aboveand below an N channel 850 that couples the source 815 to the drain 820of the JFET 810. The bottom gate 845 is bounded by two P wells 855 thatprovide an electrical connection to the bottom gate 845. The JFET 810 isdisposed within an N well region that comprises two N wells 860 and an Nisolation layer 865. The P wells 855 also serve to isolate the N channel850 from the N wells 860 in these embodiments.

As shown in FIG. 8A, a gate 870 of the MOSFET 805 is controlled by asignal V_(g1). Similarly, the top gate 840 and bottom gate 845 of theJFET 810 are controlled by signals V_(g2) and V_(g3), respectively. Asnoted above, the signal V_(g2) may be dependent upon, or independent of,the signal V_(g1). Additionally, the signal V_(g3) may be dependentupon, or independent of, the signal V_(g2).

FIG. 8B provides a cross section of another exemplary electronic circuit877 comprising a MOSFET 805 and a dual-gate JFET 810 where the MOSFET805 and the JFET 810 comprise distinct transistors. In circuit 875 eachof the MOSFET 805 and the dual-gate JFET 810 are disposed withinseparate N well regions. Here, the N well region within which the MOSFET805 is disposed is bounded by two N wells 880 and an N isolation layer885. These embodiments advantageously isolate the MOSFET 805 from thesubstrate of the JFET 810.

FIG. 9 provides a circuit diagram for an exemplary electronic circuit900 that comprises the electronic circuit 700 and further comprises a DCbias source 910 coupled to the top and bottom gates 725, 730. Inoperation, a DC bias voltage is added to the input signal to control thetop and bottom gates 725, 730. The DC bias voltage can be positive ornegative, in various embodiments. A negative gate voltage can be appliedon the top and bottom gates 725, 730 to decrease the common nodevoltage, ensuring in this way that the drain of the MOSFET 805 remainsin its reliable zone. On the contrary, a positive voltage can be appliedon the top and bottom gates 725, 730 to use the complete excursion ofthe reliable drain voltage to increase performance. In embodiments suchas electronic circuit 900, and in those embodiments described below, theMOS and JFET gate circuit 745 and the common node circuit 750 are bothoptional.

FIG. 10 provides a circuit diagram for an exemplary electronic circuit1000 that comprises the electronic circuit 700 and further comprises afirst DC bias source 1010 coupled to the top gate 725 and a second DCbias source 1020 coupled to the bottom gate 730. In operation,independent DC bias voltages are added to the input signal toindependently control each of the top and bottom gates 725, 730. Each DCbias voltage can be positive or negative, in various embodiments. Acapacitor 1030 is added between both top and bottom gates 725, 730 toallow a different DC bias to be applied to each, while applying the sameRF coupling to each of the top and bottom gates 725, 730 as is appliedto the gate of the MOSFET 705.

FIG. 11 provides a circuit diagram for an exemplary electronic circuit1100 that comprises the electronic circuit 700 but without the MOS andJFET gate circuit 745 and wherein the top gate 725 and the bottom gate730 are both coupled to ground.

FIG. 12 provides a circuit diagram for an exemplary electronic circuit1200 that comprises the electronic circuit 700 but without the MOS andJFET gate circuit 745 and wherein the top gate 725 and the bottom gate730 are both coupled to the DC bias source 910. The DC bias voltage canbe positive or negative, in various embodiments.

FIG. 13 provides a circuit diagram for an exemplary electronic circuit1300 that comprises the electronic circuit 700 but without the MOS andJFET gate circuit 745. Additionally, as opposed to FIG. 7, the first DCbias source 1010 is coupled to the top gate 725 and the second DC biassource 1020 is coupled to the bottom gate 730 rather than the top andbottom gates 725, 730 being dependent. Each DC bias voltage can bepositive or negative, in various embodiments. In those embodimentsillustrated by FIGS. 11-13 control of the top and bottom gates 725, 730is independent of the input signal.

FIG. 14 provides a circuit diagram for an exemplary electronic circuit1400 that comprises the electronic circuit 1300 and further comprisesthe MOS and JFET gate circuit 745. FIG. 15 provides a circuit diagramfor an exemplary electronic circuit 1500 that comprises the electroniccircuit 700, modified such that the bottom gate 730 is independent ofthe top gate 725, and further comprising the DC bias source 910 coupledto the top gate 725 while the bottom gate 730 is coupled to ground. Inthose embodiments illustrated by FIGS. 14 and 15 control of the top gate725 is dependent upon the input signal while control of the bottom gate730 is independent of the input signal. An advantage to only applyingthe RF signal to the top gate 725 of the JFET 710 is that thecapacitance between top gate 725 and drain or source terminals issmaller than the capacitances between the bottom gate 730 and the sourceor drain terminals, and that the top gate 725 is more efficient than thebottom gate 730 for controlling the channel current flow.

FIG. 16 provides a flowchart representation of an exemplary method 1600for amplifying a signal with a MOSFET 705 in a cascode configurationwith a dual-gate JFET 710. The method comprises a step 1610 ofcontrolling a gate of a MOSFET with a first signal, namely, the inputsignal to be amplified, a step 1620 of controlling a top gate of a JFETwith a second signal, and a step 1630 of controlling a bottom gate ofthe JFET with a third signal. It will be appreciated that the stepsillustrated by FIG. 16 are intended to be performed concurrently.

In various embodiments, the second signal is dependent upon the firstsignal and in some of these embodiments the two signals are the same,for example, where the gate of the MOSFET and the top gate of the JFETare capacitively coupled. In some of these embodiments the third signalis also dependent on the first and second signals, such as isillustrated by FIG. 7, while in other embodiments the third signal isindependent of the first and second signals, such as in FIGS. 14 and 15.

In various embodiments the second signal is independent of the firstsignal, such as is illustrated by FIGS. 11-13. In some of theseembodiments the third signal is dependent upon the second signal whilein other embodiments the third signal is independent of the secondsignal.

In various embodiments the first signal comprises the sum of the inputsignal and a DC bias. Also in various embodiments either or both of thesecond and third signals can be a fixed DC bias, either positive ornegative, or ground.

The embodiments discussed herein are illustrative of the presentinvention. As these embodiments are described with reference toillustrations, various modifications or adaptations of the methods orspecific elements described may become apparent to those skilled in theart. All such modifications, adaptations, or variations that rely on theteachings of the present invention, and through which these teachingshave advanced the art, are considered to be in the spirit and scope ofthe present invention. Hence, these descriptions and drawings should notbe considered in a limiting sense, as it is understood that the presentinvention is in no way limited to only the embodiments illustrated.

1. An electronic circuit comprising: a MOSFET including a source, adrain, and a gate; and a JFET, distinct from the MOSFET, and including asource, a drain, a top gate, and a bottom gate, the source of the JFETbeing directly coupled to the drain of the MOSFET and wherein the topgate of the JFET is coupled to the gate of the MOSFET and the bottomgate of the JFET is also coupled to the gate of the MOSFET.
 2. Theelectronic circuit of claim 1 wherein the top gate of the JFET iscoupled to the gate of the MOSFET by a JFET gate circuit.
 3. Theelectronic circuit of claim 1 wherein the gates of the MOSFET and of theJFET have different widths.
 4. The electronic circuit of claim 1 whereinthe top and bottom gates of the JFET are both coupled to a DC biassource.
 5. An electronic circuit comprising: a MOSFET including asource, a drain, and a gate; and a JFET, distinct from the MOSFET, andincluding a source, a drain, a top gate, and a bottom gate, the sourceof the JFET being directly coupled to the drain of the MOSFET andwherein the top gate of the JFET is coupled to the bottom gate of theJFET.
 6. The electronic circuit of claim 5 wherein the top gate of theJFET is capacitively coupled to the bottom gate of the JFET.
 7. Theelectronic circuit of claim 5 wherein the top and bottom gates of theJFET are both coupled to a DC bias source.
 8. The electronic circuit ofclaim 5 wherein the top and bottom gates of the JFET are both coupled toground.
 9. An electronic circuit comprising: a MOSFET including asource, a drain, and a gate; and a JFET, distinct from the MOSFET, andincluding a source, a drain, a top gate, and a bottom gate, the sourceof the JFET being directly coupled to the drain of the MOSFET, the topgate of the JFET being coupled to the bottom gate of the JFET, andwherein the top gate of the JFET is independent of the gate of theMOSFET.